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pin connections rev. d information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. a dual single-supply audio operational amplifier ssm2135 one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 617/329-4700 fax: 617/326-8703 features excellent sonic characteristics high output drive capability 5.2 nv/ ? hz equivalent input noise @ 1 khz 0.001% thd+n (v o = 2.5 v p-p @ 1 khz) 3.5 mhz gain bandwidth unity-gain stable low cost applications multimedia audio systems microphone preamplifier headphone driver differential line receiver balanced line driver audio adc input buffer audio dac l-v converter and filter pseudo-ground generator general description the ssm2135 dual audio operational amplifier permits excellent performance in portable or low power audio systems, with an operating supply range of +4 v to +36 v or 2 v to 18 v. the unity gain stable device has very low voltage noise of 4.7 nv/ ? hz , and total harmonic distortion plus noise below 0.01% over normal signal levels and loads. such characteristics are enhanced by wide output swing and load drive capability. a unique output stage* permits output swing approaching the rail under moderate load conditions. under severe loading, the ssm2135 still maintains a wide output swing with ultralow distortion. particularly well suited for computer audio systems and portable digital audio units, the ssm2135 can perform preamplification, headphone and speaker driving, and balanced line driving and receiving. additionally, the device is ideal for input signal conditioning in single-supply sigma-delta analog- to-digital converter subsystems such as the ad1878/ad1879. the ssm2135 is available in 8-lead plastic dip and soic packages, and is guaranteed for operation over the extended industrial temperature range of C40 c to +85 c. *protected by u. s. patent no. 5,146,181. ssm2135 v+ out b ?n b +in b out a ?n a +in a v?gnd ssm2135 out a ?n a +in a v?gnd 1 2 3 4 8 7 6 5 v+ out b ?n b +in b (s suffix) (p-suffix) 8-lead narrow-body soic 8-lead epoxy dip functional block diagram 9v 9v +in ?n out v+ v?gnd
rev. d C2C ssm2135Cspecifications parameter symbol conditions min typ max units audio performance voltage noise density e n f = 1 khz 5.2 nv/ ? hz current noise density i n f = 1 khz 0.5 pa/ ? hz signal-to-noise ratio snr 20 hz to 20 khz, 0 dbu = 0.775 v rms 121 dbu headroom hr clip point = 1% thd+n, f = 1 khz, r l = 10 k w 5.3 dbu total harmonic distortion thd+n a v = +1, v o = 1 v p-p, f = 1 khz, 80 khz lpf r l = 10 k w 0.003 % r l = 32 w 0.005 % dynamic performance slew rate sr r l = 2 k w , t a = +25 c 0.6 0.9 v/ m s gain bandwidth product gbw 3.5 mhz settling time t s to 0.1%, 2 v step 5.8 m s input characteristics input voltage range v cm 0 +4.0 v input offset voltage v os v out = 2 v 0.2 2.0 mv input bias current i b v cm = 0 v, v out = 2 v 300 750 na input offset current i os v cm = 0 v, v out = 2 v 50 na differential input impedance z in 4m w common-mode rejection cmr 0 v v cm 4 v, f = dc 87 112 db large signal voltage gain a vo 0.01 v v out 3.9 v, r l = 600 w 2v/ m v output characteristics output voltage swing high v oh r l = 100 k w 4.1 v r l = 600 w 3.9 v output voltage swing low v ol r l = 100 k w 3.5 mv r l = 600 w 3.0 mv short circuit current limit i sc 30 ma power supply supply voltage range v s single supply +4 +36 v dual supply 2 18 v power supply rejection ratio psrr v s = +4 v to +6 v, f = dc 90 120 db supply current i sy v out = 2.0 v, no load v s = +5 v 2.8 6.0 ma v s = 18 v, v out = 0 v, no load 3.7 7.6 ma (v s = +5 v, C40 8 c < t a < +85 8 c unless otherwise noted. typical specifications apply at t a = +25 8 c.) absolute maximum ratings supply voltage single supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +36 v dual supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 v input voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . v s differential input voltage . . . . . . . . . . . . . . . . . . . . . . . . 10 v output short circuit duration . . . . . . . . . . . . . . . . indefinite storage temperature range . . . . . . . . . . . . C65 c to +150 c operating temperature range . . . . . . . . . . . C40 c to +85 c junction temperature range (t j ) . . . . . . . . C65 c to +150 c lead temperature (soldering, 60 sec) . . . . . . . . . . . . +300 c esd ratings 883 (human body) model . . . . . . . . . . . . . . . . . . . . . . . 1 kv eiaj model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 175 v thermal characteristics thermal resistance 1 8-lead plastic dip q ja 103 c/w q jc 43 c/w 8-lead soic q ja 158 c/w q jc 43 c/w 1 q ja is specified for worst case conditions, i.e., q ja is specified for device in socket for p-dip and device soldered in circuit board for soic package. ordering guide temperature package package model range description option SSM2135P C40 c to +85 c 8-lead plastic dip n-8 ssm2135s C40 c to +85 c 8-lead soic so-8
ssm2135 rev. d C3C +5v +2.5vdc r l 500 m f + figure 1. test circuit for figures 2C4 figure 2. thd+n vs. amplitude (see test circuit; a v = +1, v s = +5 v, f = 1 khz, with 80 khz low-pass filter) figure 3. thd+n vs. frequency (see test circuit; a v = +1, v in = 1 v p-p, with 80 khz low-pass filter) 10 0.1 0.001 10 100 10k 1k 1 0.01 load resistance ? w thd ?% v s = +5v a v = +1, | = 1khz v in = 1vp-p r l = 10k w with 80khz filter figure 4. thd+n vs. load (see test circuit) 1 0.001 020 60 40 0.01 10 0.1 30 50 v s = +5v r l = 100k w v out = 2.5vp-p | = 1khz with 80khz filter gain db thd+n ?% noninverting inverting figure 5. thd+n vs. gain 1 0.01 0.001 10 30 20 0.1 supply voltage ?v thd+n ?% v s = +5v a v = +1, | = 1khz v in = 1vp-p r l = 10k w with 80khz filter 51525 figure 6. thd+n vs. supply voltage
ssm2135 rev. d C4C figure 7. smpte intermodulation distortion (a v = +1, v s = +5 v, f = 1 khz, r l = 10 k w ) 10 0% 100 90 1s figure 8. input voltage noise (20 nv/div) 30 15 0 110 1k 100 5 20 25 frequency hz v s = +5v t a = +25 c 10 e n ?nv/ ? hz figure 9. voltage noise density vs. frequency 5 2 0 110 1k 100 1 3 4 frequency hz v s = +5v t a = +25 c i n ?pa/ ? hz figure 10. current noise density vs. frequency figure 11. frequency response (a v = +1, v s = +5 v, v in = 1 v p-p, r l = 10 k w ) 10 100 0% 90 1 m s 500m v figure 12. square wave response (v s = +5 v, a v = +1, r l = )
ssm2135 rev. d C5C 10 100 10m 1m 100k 10k 1k frequency ?hz 105 60 40 20 0 ?0 ?0 ?0 ?0 ?00 ?20 channel separation ?db v s = +5v t a = +25 c figure 13. crosstalk vs. frequency (r l = 10 k w ) 140 100 0 1k 1m 100k 10k 100 120 60 80 20 40 frequency ?hz common-mode rejection ?db v s = +5v t a = +25 c figure 14. common-mode rejection vs. frequency 140 60 ?0 10 100 1m 100k 10k 1k 80 100 120 0 20 40 frequency hz v s = +5v a v = +1 t a = +25 c psrr ?db +psrr ?srr figure 15. power supply rejection vs. frequency 50 30 ?0 10k 10m 1m 100k 1k 40 10 20 ?0 0 frequency ?hz closed-loop gain ?db v s = +5v t a = +25 c a v = +100 a v = +10 a v = +1 figure 16. closed-loop gain vs. frequency 100 40 ?0 10k 10m 1m 100k 1k 20 0 60 80 frequency ?hz open-loop gain ?db 90 225 135 180 45 0 phase ?degrees v s = +5v t a = +25 c gain phase q m = 57 figure 17. open-loop gain and phase vs. frequency 50 0 500 15 5 100 10 0 30 20 25 35 40 45 400 300 200 load capacitance ?pf overshoot ?% negative edge positive edge v s = +5v r l = 2k w v in = 100mvp? t a = +25 c a v = +1 figure 18. small signal overshoot vs. load capacitance
ssm2135 rev. d C6C frequency hz 50 25 0 10 100 1m 100k 10k 1k 30 35 40 45 5 10 15 20 v s = +5v t a = +25 c impedance ? w a vcl = +100 a vcl = +1 a vcl = +10 figure 19. output impedance vs. frequency 5 4 0 1 10 100k 10k 1k 100 3 2 1 v s = +5v t a = +25 c a v = +1 | = 1khz thd+n = 1% load resistance ? w maximum output ?volts figure 20. maximum output voltage vs. load resistance 6 3 0 10k 10m 1m 100k 1k 2 1 4 5 frequency ?hz maximum output swing ?volts v s = +5v r l = 2k w t a = +25 c a v = +1 figure 21. maximum output swing vs. frequency 40 20 0 05 40 35 30 25 20 15 10 25 30 35 5 10 15 v s = +5v a v = +1 r l = 10k | = 1khz thd+n = 1% t a = +25 c supply voltage ?volts output voltage ?volts figure 22. output swing vs. supply voltage 5.0 3.0 125 4.5 3.5 ?0 4.0 75 100 50 25 0 ?5 temperature ? c positive output swing ?volts v s = +5.0v 2.0 0 1.5 0.5 1.0 negative output swing ?volts +swing r l = 2k w +swing r l = 600 w ?wing r l = 2k w ?wing r l = 600 w ?5 figure 23. output swing vs. temperature and load 2.0 0 125 1.5 0.5 ?0 1.0 75 100 50 25 0 ?5 temperature ? c slew rate ?v/ m s v s = +5v +0.5v v out +4.0v ?lew rate +slew rate ?5 figure 24. slew rate vs. temperature
ssm2135 rev. d C7C 5 0 125 3 1 ?0 2 4 100 75 50 25 0 ?5 temperature ? c supply current ?ma v s = 18v v s = 15v v s = +5.0v ?5 figure 27. supply current vs. temperature 500 0 125 300 100 ?0 200 400 100 75 50 25 0 ?5 temperature ? c input bias current ?na v s = 15v v s = +5.0v ?5 figure 28. input bias current vs. temperature 20 0 125 6 2 ?0 4 12 8 10 14 16 18 100 75 50 25 0 ?5 temperature ? c open-loop gain ?v/ m v r l = 2k w r l = 600 w v s = +5.0v v o = 3.9v ?5 figure 25. open-loop gain vs. temperature 70 50 125 65 55 ?0 60 75 100 50 25 0 ?5 temperature ? c phase margin ?degrees v s = +5v 5 1 4 2 3 gain-bandwidth product ?mhz ?5 gbw q m figure 26. gain bandwidth product and phase margin vs. temperature application information the ssm2135 is a low voltage audio amplifier that has exceptionally low noise and excellent sonic quality even when driving loads as small as 25 w . designed for single supply use, the ssm2135s inputs common-mode and output swing to zero volts. thus with a supply voltage at +5 v, both the input and output will swing from 0 v to +4 v. because of this, signal dynamic range can be optimized if the amplifier is biased to a +2 v reference rather than at half the supply voltage. the ssm2135 is unity-gain stable, even when driving into a fair amount of capacitive load. driving up to 500 pf does not cause any instability in the amplifier. however, overshoot in the frequency response increases slightly. the ssm2135 makes an excellent output amplifier for +5 v only audio systems such as a multimedia workstation, a cd output amplifier, or an audio mixing system. the amplifier has large output swing even at this supply voltage because it is designed to swing to the negative rail. in addition, it easily drives load impedances as low as 25 w with low distortion. the ssm2135 is fully protected from phase reversal for inputs going to the negative supply rail. however, an internal esd protection diodes will turn on when either input is forced more than 0.5 v below the negative rail. under this condition, input current in excess of 2 ma may cause erratic output behavior, in which case a current limiting resistor should be included in the offending input if phase integrity is required with excessive input voltages. a 500 w or higher series input resistor will prevent phase inversion even with the input pulled 1 volt below the negative supply. hot plugging the input to a signal generally does not present a problem for the ssm2135, assuming the signal does not have any voltage exceeding the devices supply voltage. if so, it is advisable to add a series input resistor to limit the current, as well as a zener diode to clamp the input to a voltage no higher than the supply.
ssm2135 rev. d C8C application circuits a low noise stereo headphone driver amplifier figure 29 shows the ssm2135 used in a stereo headphone driver for multimedia applications with the ad1848, a 16-bit stereo codec. the ssm2135 is equally well suited for the serial- bused ad1849 stereo codec. the headphones impedance can be as low as 25 w , which covers most commercially available high fidelity headphones. although the amplifier can operate at up to 18 v supply, it is just as efficient powered by a single +5 v. at this voltage, the amplifier has sufficient output drive to deliver distortion-free sound to a low impedance headphone. 10? 4 6 5 8 7 0.1? 1/2 ssm2135 10? +5v 1/2 ssm2135 0.1? 1 2 3 8.66k w 10k w 0.1? 40 35/36 32 41 l ch r ch agnd 34/37 8.66k w 10k w v cc gnd v ref r out ad1848 l out 470? 470? figure 29. a stereo headphone driver for multimedia sound codec figure 30 shows the total harmonic distortion characteristics versus frequency driving into a 32 w load, which is a very typical impedance for a high quality stereo headphone. the ssm2135 has excellent power supply rejection, and as a result, is tolerant of poorly regulated supplies. however, for best sonic quality, the power supply should be well regulated and heavily bypassed to minimize supply modulation under heavy loads. a minimum of 10 m f bypass is recommended. figure 30. headphone driver thd+n vs. frequency into a 32 w load (v s = +5 v, with 80 khz low-pass filter) a low noise microphone preamplifier the ssm2135s 4.7 nv/ ? hz input noise in conjunction with low distortion makes it an ideal device for amplifying low level signals such as those produced by microphones. figure 31 illus- trates a stereo microphone input circuit feeding a multimedia sound codec. as shown, the gain is set at 100 (40 db), although it can be set to other gains depending on the microphone output levels. figure 32 shows the preamplifiers harmonic distortion performance with 1 v rms output while operating from a single +5 v supply. the ssm2135 is biased to 2.25 v by the v ref pin of the ad1848 codec. the same voltage is buffered by the 2n4124 transistor to provide phantom power to the microphone. a typical electret condenser microphone with an impedance range of 100 w to 1 k w works well with the circuit. this power booster circuit may be omitted for dynamic microphone elements. l channel mic in 10? 4 6 5 8 7 10? 1/2 ssm2135 10? +5v 1/2 ssm2135 0.1? 1 2 3 10k w 10k w 100 w r channel mic in 100 w 0.1? 29 35/36 34/37 +5v lmic v cc gnd v ref rmic ad1848 32 28 10k w 10k w +5v 2n4124 10? 2k w 2k w figure 31. low noise microphone preamp for multimedia sound codec figure 32. mic preamp thd+n performance (v s = +5 v, a v = 40 db, v out = 1 v rms, with 80 khz low-pass filter)
ssm2135 rev. d C9C an 18-bit stereo cd-dac output amplifier the ssm2135 makes an ideal single supply stereo output amplifier for audio d/a converters because of its low noise and distortion. figure 33 shows the implementation of an 18-bit ste- reo dac channel. the output amplifier also provides low-pass filtering for smoothing the oversampled audio signal. the filters cutoff frequency is set at 22.5 khz and it has a maximally flat response from dc to 20 khz. as mentioned above, the amplifiers outputs can drive directly into a stereo headphone that has impedance as low as 25 w with no additional buffering required. 6 7 5 100pf 330pf 16 15 14 13 12 11 10 9 18-bit dac v ref 18-bit serial reg. vol agnd 18-bit serial reg. 18-bit dac v ref vor vbl dgnd vbr lr dr ll dl ck v l v s 1 2 3 4 5 6 7 8 ad1868 220 m f 47k w right channel output 330pf 100pf 220 m f left channel output +5v s upply 1 3 2 4 8 1/2 ssm2135 1/2 ssm2135 47k w 7.68k w 7.68k w 7.68k w 7.68k w 9.76k w 9.76k w figure 33. +5 v stereo 18-bit dac a single supply differential line driver signal distribution and routing is often required in audio systems, particularly portable digital audio equipment for professional applications. figure 34 shows a single supply line driver circuit that has differential output. the bottom amplifier provides a 2 v dc bias for the differential amplifier in order to maximize the output swing range. the amplifier can output a maximum of 0.8 v rms signal with a +5 v supply. it is capable of driving into 600 w line termination at a reduced output amplitude. 1? 6 5 8 7 1/2 ssm2135 0.1? 100 w 1/2 ssm2135 1 2 3 10?+0.1? +5v 4 1k w 8 1 3 2 4 differential audio out 2.5k w 7.5k w 5k w +5v 10k w 2.0v 1k w +5v 1/2 ssm2135 1k w 100? audio in figure 34. single supply differential line driver a single supply differential line receiver receiving a differential signal with minimum distortion is achieved using the circuit in figure 35. unlike a difference amplifier (a subtractor), the circuit has a true balanced input impedance regardless of input drive levels. that is, each input always presents a 20 k w impedance to the source. for best common-mode rejection performance, all resistors around the differential amplifier must be very well matched. best results can be achieved using a 10 k w precision resistor network. 1? 6 5 8 7 1/2 ssm2135 10? +5v 0.1? 20k w 1/2 ssm2135 1 2 3 10?+0.1? +5v 4 2.0v 1/2 ssm2135 differential audio in 8 1 3 2 4 +5v 2.5k w audio out 20k w 20k w 10k w 10k w 100 w 5k w 7.5k w 10 w figure 35. single supply balanced differential line receiver a pseudo-reference voltage generator for single supply circuits, a reference voltage source is often required for biasing purposes or signal offsetting purposes. the circuit in figure 36 provides a supply splitter function with low output impedance. the 1 m f output capacitor serves as a charge reservoir to handle a sudden surge in demand by the load as well as providing a low ac impedance to it. the 0.1 m f feedback capacitor compensates the amplifier in the presence of a heavy capacitive load, maintaining stability. the output can source or sink up to 12 ma of current with +5 v supply, limited only by the 100 w output resistor. reduc- ing the resistance will increase the output current capability. alternatively, increasing the supply voltage to 12 v also improves the output drive to more than 25 ma. c1 0.1? r2 5k w c2 1? r4 100 w output v s + 2 1/2 ssm2135 1 8 4 2 r3 2.5k w 3 r1 5k w v s + = +5v ? +12v figure 36. pseudo-reference generator
ssm2135 rev. d C10C a digital volume control circuit working in conjunction with the ad7528/pm7528 dual 8-bit d/a converter, the ssm2135 makes for an efficient audio attenuator, as shown in figure 37. the circuit works off a single +5 v supply. the dacs are biased to a 2 v reference level which is sufficient to keep the dacs internal r-2r ladder switches operating properly. this voltage is also the optimal midpoint of the ssm2135s common-mode and output swing range. with the circuit as shown, the maximum input and output swing is 1.25 v rms. total harmonic distortion measures a respectable 0.01% at 1 khz and 0.1% at 20 khz. the fre- quency response at any attenuation level is flat to 20 khz. each dac can be controlled independently via the 8-bit parallel data bus. the attenuation level is linearly controlled by the binary weighting of the digital data input. total attenuation ranges from 0 db to 48 db. 1? 47? 8 47? 2k w 100 w 0.1? 1/2 ssm2135 1 2 3 10?+0.1? +5v 4 1/2 ssm2135 8 1 3 2 4 +5v 5k w l audio out 47? 1/2 ssm2135 r audio out 6 5 7 2.0v 7.5k w +5v 2.0v 3 2 19 20 1 17 5 18 4 6 15 16 daca/ dacb cs wr ref b dac b fb outb v dd dgnd 0.1? +5v 47? l audio in data in control signal r audio in ad/pm-7528 ref a dac a fb outa figure 37. digital volume control a logarithmic volume control circuit figure 38 shows a logarithmic version of the volume control function. similar biasing is used. with an 8-bit bus, the ad7111 provides an 88.5 db attenuation range. each bit resolves a 0.375 db attenuation. refer to ad7111 data sheet for attenuation levels for each input code. 1? 8 47? 2k w 100 w 0.1? 1/2 ssm2135 1 2 3 4 1/2 ssm2135 8 1 3 2 4 +5v 5k w l audio out 47? 1/2 ssm2135 r audio out 6 5 7 7.5k w +5v 2.0v 0.1? +5v l audio in data in & control r audio in 10?+0.1? +5v 1 2 15 31416 47? dgnd ad7111 fb outa v dd agnd v in 1 2 0.1? +5v 31416 dgnd ad7111 fb outa v dd agnd v in 15 47? 10 10 10 figure 38. single supply logarithmic volume control
ssm2135 rev. d C11C spice macromodel * ssm2135 spice macro-model 9/92, rev. a * jcb/adi *copyright 1993 by analog devices, inc. * *node assignments * * noninverting input * inverting input * positive supply * negative supply * output .subckt ssm2135 32746 * * input stage r3 4 19 1.5e3 r4 4 20 1.5e3 c1 19 20 5.311eC12 i1 7 18 106eC6 ios 2 3 25eC09 eos 12 5 poly(1) 51 4 25eC06 1 q1 19 3 18 pnp1 q2 20 12 18 pnp1 cin 3 2 3eC12 d131dy d221dy en5222 01 gn1 0 2 25 0 1eC5 gn2 0 3 28 0 1eC5 * * voltage noise source with flicker noise dn1 21 22 den dn2 22 23 den vn1 21 0 dc 2 vn2 0 23 dc 2 * * current noise source with flicker noise dn3 24 25 din dn4 25 26 din vn3 24 0 dc 2 vn4 0 26 dc 2 * * second current noise source dn5 27 28 din dn6 28 29 din vn5 27 0 dc 2 vn6 0 29 dc 2 * * gain stage & dominant pole at .2000e+01 hz g2 34 36 19 20 2.65eC04 r7 34 36 39e+06 v3 35 4 dc 6 d4 36 35 dx vb2 34 4 1.6 * * supply/2 generator isy 7 4 0.2eC3 r10 7 60 40e+3 r11 60 4 40e+3 c3 60 0 1eC9 * * cmrr stage & pole at 6 khz ecm 50 4 poly(2) 3 60 2 60 0 1.6 1.6 ccm 50 51 26.5eC12 rcm1 50 51 1e6 rcm2 51 4 1 * * output stage r12 37 36 1e3 r13 38 36 500 c4 37 6 20eC12 c5 38 39 20eC12 m1 39 36 4 4 mn l=9eC6 w=1000eC6 ad=15eC9 as=15eC9 m2 45 36 4 4 mn l=9eC6 w=1000eC6 ad=15eC9 as=15eC9 5 3947dx d6 47 45 dx q3 39 40 41 qpa 8 vb 7 40 dc 0.861 r14 7 41 375 q4 41 7 43 qna 1 r17 7 43 15 q5 43 39 6 qna 20 q6 46 45 6 qpa 20 r18 46 4 15 q7 36 46 4 qna 1 m3 6 36 4 4 mn l=9eC6 w=2000eC6 ad=30eC9 as=30eC9 * * nonlinear models used * .model dx d (is=1eC15) .model dy d (is=1eC15 bv=7) .model pnp1 pnp (bf=220) .model den d(is=1eC12 rs=1016 kf=3.278eC15 af=1) .model din d(is=1eC12 rs=100019 kf=4.173eC15 af=1) .model qna npn(is=1.19eC16 bf=253 vaf=193 var=15 rb=2.0e3 + irb=7.73eC6 rbm=132.8 re=4 rc=209 cje=2.1eC13 vje=0.573 + mje =0.364 cjc=1.64eC13 vjc=0.534 mjc=0.5 cjs=1.37eC12 + vjs=0.59 mjs=0.5 tf=0.43eC9 ptf=30) .model qpa pnp(is=5.21eC17 bf=131 vaf=62 var=15 rb=1.52e3 + irb=1.67e 5Crbm=368.5 re=6.31 rc=354.4 cje=1.1eC13 + vje=0.745 mje=0.33 cjc=2.37eC13 vjc=0.762 mjc=0.4 + cjs=7.11eC13 vjs=0.45 mjs=0.412 tf=1.0eC9 ptf=30) .model mn nmos(level=3 vto=1.3 rs=0.3 rd=0.3 tox=8.5eC8 + ld=1.48eC6wd=1eC6 nsub=1.53e16uo=650 delta= 10vmax=2e5 + xj=1.75 eC6 kappa=0.8 eta=0.066 the ta=0.01tpg=1 cj=2.9eC4 + pb=0.837 mj=0.407 cjsw=0.5eC9 mjsw=0.33) * .ends ssm-2135
ssm2135 rev. d C12C outline dimensions dimensions shown in inches and (mm). c1772aC10C10/97 printed in u.s.a. 8-lead plastic dip (n-8) 0.160 (4.06) 0.115 (2.93) 0.130 (3.30) min 0.210 (5.33) max 0.015 (0.381) typ 0.430 (10.92) 0.348 (8.84) 0.280 (7.11) 0.240 (6.10) 4 5 8 1 0.070 (1.77) 0.045 (1.15) 0.022 (0.558) 0.014 (0.356) 0.325 (8.25) 0.300 (7.62) 0? 15? 0.100 (2.54) bsc 0.015 (0.381) 0.008 (0.204) seating plane 0.195 (4.95) 0.115 (2.93) 8-lead narrow-body (so-8) seating plane 4 5 8 1 0.0688 (1.75) 0.0532 (1.35) 0.1574 (4.00) 0.1497 (3.80) 0.2440 (6.20) 0.2284 (5.80) 0.1968 (5.00) 0.1890 (4.80) 0.0192 (0.49) 0.0138 (0.35) 0.0500 (1.27) bsc 0.0098 (0.25) 0.0040 (0.10) 0.0098 (0.25) 0.0075 (0.19) 45 0.0196 (0.50) 0.0099 (0.25) 0.0500 (1.27) 0.0160 (0.41) 0 - 8

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